# TLVx369 Cost-Optimized, 800-nA, 1.8-V, Rail-to-Rail I/O Operational Amplifier with Zero-Crossover Distortion

SBOS757 – May2016

**PRODUCTION DATA. **

## 8 Application and Implementation

NOTE

Information in the following applications sections is not part of the TI component specification, and TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining suitability of components for their purposes. Customers should validate and test their design implementation to confirm system functionality.

### 8.1 Application Information

When designing for ultra-low power, choose system components carefully. To minimize current consumption, select large-value resistors. Any resistors can react with stray capacitance in the circuit and the input capacitance of the operational amplifier. These parasitic RC combinations can affect the stability of the overall system. Use of a feedback capacitor assures stability and limits overshoot or gain peaking.

### 8.2 Typical Application

A typical application for an operational amplifier is an inverting amplifier, as shown in Figure 15. An inverting amplifier takes a positive voltage on the input and outputs a signal inverted to the input, making a negative voltage of the same magnitude. In the same manner, the amplifier also makes negative input voltages positive on the output. In addition, amplification can be added by selecting the input resistor R_{I} and the feedback resistor R_{F}.

#### 8.2.1 Design Requirements

The supply voltage must be chosen to be larger than the input voltage range and the desired output range. The limits of the input common-mode range (V_{CM}) and the output voltage swing to the rails (V_{O}) must also be considered. For instance, this application scales a signal of ±0.5 V (1 V) to ±1.8 V (3.6 V). Setting the supply at ±2.5 V is sufficient to accommodate this application.

#### 8.2.2 Detailed Design Procedure

Determine the gain required by the inverting amplifier using Equation 1 and Equation 2:

When the desired gain is determined, choose a value for R_{I} or R_{F}. Choosing a value in the kilohm range is desirable for general-purpose applications because the amplifier circuit uses currents in the milliamp range. This milliamp current range ensures that the device does not draw too much current. The trade-off is that very large resistors (100s of kilohms) draw the smallest current but generate the highest noise. Very small resistors (100s of ohms) generate low noise but draw high current. This example uses 10 kΩ for R_{I}, meaning 36 kΩ is used for R_{F}. These values are determined by Equation 3:

#### 8.2.3 Application Curve

### 8.3 System Examples

#### 8.3.1 Battery Monitoring

The low operating voltage and quiescent current of the TLV369 series make the family an excellent choice for battery-monitoring applications, as shown in Figure 17.

In this circuit, V_{STATUS} is high as long as the battery voltage remains above 2 V. A low-power reference is used to set the trip point. Resistor values are selected as follows:

- Selecting R
_{F}: Select R_{F}such that the current through R_{F}is approximately 1000 times larger than the maximum bias current over temperature, as given by Equation 4: - Choose the hysteresis voltage, V
_{HYST}. For battery-monitoring applications, 50 mV is adequate. - Calculate R
_{1}as calculated by Equation 5: - Select a threshold voltage for V
_{IN}rising (V_{THRS}) = 2.0 V. - Calculate R
_{2}as given by Equation 6: - Calculate R
_{BIAS}: The minimum supply voltage for this circuit is 1.8 V. The REF1112 has a current requirement of 1.2 μA (max). Providing the REF1112 with 2 μA of supply current assures proper operation. Therefore, R_{BIAS}is as given by Equation 7.

#### 8.3.2 Window Comparator

Figure 18 shows the TLV2369 used as a window comparator. The threshold limits are set by V_{H} and V_{L}, with V_{H} greater than V_{L}. When V_{IN} is less than V_{H}, the output of A1 is low. When V_{IN} is greater than V_{L}, the output of A2 is low. Therefore, both op amp outputs are at 0 V as long as V_{IN} is between V_{H} and V_{L}. This architecture results in no current flowing through either diode, Q1 is in cutoff, with the base voltage at 0 V, and V_{OUT} forced high.

If V_{IN} falls below V_{L}, the output of A2 is high, current flows through D2, and V_{OUT} is low. Likewise, if V_{IN} rises above V_{H}, the output of A1 is high, current flows through D1, and V_{OUT} is low. The window comparator threshold voltages are set as shown by Equation 8 and Equation 9:

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