SNOS405B November   1999  – May 2017 MAX660

PRODUCTION DATA.  

  1. Features
  2. Applications
  3. Description
  4. Revision History
  5. Pin Configuration and Functions
  6. Specifications
    1. 6.1 Absolute Maximum Ratings
    2. 6.2 ESD Ratings
    3. 6.3 Recommended Operating Conditions
    4. 6.4 Thermal Information
    5. 6.5 Electrical Characteristics
    6. 6.6 Typical Characteristics
  7. Parameter Measurement Information
    1. 7.1 MAX660 Test Circuit
  8. Detailed Description
    1. 8.1 Overview
    2. 8.2 Functional Block Diagram
    3. 8.3 Feature Description
    4. 8.4 Device Functional Modes
  9. Application and Implementation
    1. 9.1 Application Information
    2. 9.2 Typical Applications
      1. 9.2.1 Voltage Inverter
        1. 9.2.1.1 Design Requirements
        2. 9.2.1.2 Detailed Design Procedure
          1. 9.2.1.2.1 Capacitor Selection
          2. 9.2.1.2.2 Paralleling Devices
          3. 9.2.1.2.3 Cascading Devices
          4. 9.2.1.2.4 Regulating Output Voltage
        3. 9.2.1.3 Application Curves
      2. 9.2.2 Positive Voltage Doubler
        1. 9.2.2.1 Design Requirements
        2. 9.2.2.2 Detailed Design Procedure
    3. 9.3 Split V+ in Half
  10. 10Power Supply Recommendations
  11. 11Layout
    1. 11.1 Layout Guidelines
    2. 11.2 Layout Example
  12. 12Device and Documentation Support
    1. 12.1 Device Support
      1. 12.1.1 Third-Party Products Disclaimer
    2. 12.2 Receiving Notification of Documentation Updates
    3. 12.3 Community Resources
    4. 12.4 Trademarks
    5. 12.5 Electrostatic Discharge Caution
    6. 12.6 Glossary
  13. 13Mechanical, Packaging, and Orderable Information

Package Options

Mechanical Data (Package|Pins)
Thermal pad, mechanical data (Package|Pins)
Orderable Information

Application and Implementation

NOTE

Information in the following applications sections is not part of the TI component specification, and TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining suitability of components for their purposes. Customers should validate and test their design implementation to confirm system functionality.

Application Information

The MAX660 CMOS charge-pump voltage converter is a versatile, unregulated switched-capacitor inverter or doubler. Operating from a wide 1.5-V to 5.5-V supply voltage, the MAX660 uses two low-cost capacitors to provide 100 mA of output current without the cost, size, and EMI related to inductor-based converters. With an operating current of only 120 µA and operating efficiency greater than 90% at most loads, the MAX660 provides ideal performance for battery-powered systems. MAX660 devices can be operated directly in parallel to lower output impedance, thus providing more current at a given voltage.

Typical Applications

Voltage Inverter

MAX660 10089801.png Figure 14. MAX660 Voltage Inverter

Design Requirements

For typical switched capacitor applications, use the parameters in Table 2:

Table 2. Design Parameters

DESIGN PARAMETER EXAMPLE VALUE
Input voltage 5.5 V (maximum)
Negative output voltage –1.5 V to –5.5 V
Output current 100 mA

Detailed Design Procedure

The main application of MAX660 is to generate a negative supply voltage. The voltage inverter circuit uses only two external capacitors as shown in the Figure 14. The range of the input supply voltage is 1.5 V to 5.5 V. For a supply voltage less than 3.5 V, the LV pin must be connected to ground to bypass the internal regulator circuitry. This gives the best performance in low-voltage applications. If the supply voltage is greater than 3.5 V, LV may be connected to ground or left open. The choice of leaving LV open simplifies the direct substitution of the MAX660 for the LMC7660 switched capacitor voltage converter.

The output characteristics of this circuit can be approximated by an ideal voltage source in series with a resistor. The voltage source equals −(V+). The output resistance Rout is a function of the ON resistance of the internal MOS switches, the oscillator frequency, and the capacitance and ESR of C1 and C2. A good approximation is:

Equation 1. MAX660 eq1_snos405.png

where

  • RSW is the sum of the ON resistance of the internal MOS switches shown in Figure 13.

High-value, low-ESR capacitors reduce the output resistance. Instead of increasing the capacitance, the oscillator frequency can be increased to reduce the 2/(ƒOSCc × C1) term. Once this term is trivial compared with RSW and ESRs, further increase to oscillator frequency and capacitance become ineffective. The peak-to-peak output voltage ripple is determined by the oscillator frequency, and the capacitance and ESR of the output capacitor C2:

Equation 2. MAX660 eq2_snos405.png

Again, using a low-ESR capacitor results in lower ripple.

Capacitor Selection

The output resistance and ripple voltage are dependent on the capacitance and ESR values of the external capacitors. The output voltage drop is the load current times the output resistance, and the power efficiency is shown in Equation 3:

Equation 3. MAX660 eq3_snos405.png

where

  • IQ(V+) is the quiescent power loss of the device
  • IL2ROUT is the conversion loss associated with the switch on-resistance, the two external capacitors and their ESRs

Because the switching current charging and discharging C1 is approximately twice that of the output current, the effect of the ESR of the pumping capacitor C1 is multiplied by four in the output resistance. The output capacitor C2 is charging and discharging at a current approximately equal to the output current; therefore, its ESR only counts once in the output resistance. However, the ESR of C2 directly affects the output voltage ripple. Therefore, TI recommends low-ESR capacitors (Table 3) for both capacitors to maximize efficiency, reduce the output voltage drop and voltage ripple. For convenience, C1 and C2 are usually chosen to be the same. The output resistance varies with the oscillator frequency and the capacitors. In Figure 15, the output resistance vs oscillator frequency curves are drawn for three different tantalum capacitors. At very low frequency range, capacitance plays the most important role in determining the output resistance. Once the frequency is increased to some point (such as 20 kHz for the 150-μF capacitors), the output resistance is dominated by the ON resistance of the internal switches and the ESRs of the external capacitors. A low-value, smaller size capacitor usually has a higher ESR compared with a larger size capacitor of the same type. For lower ESR, use ceramic capacitors.

MAX660 10089832.png Figure 15. Output Source Resistance vs Oscillator Frequency

Table 3. Low-ESR Capacitor Manufacturers

MANUFACTURER CAPACITOR TYPE
Nichicon Corp. PM, PJ series, through-hole aluminum electrolytic
AVX Corp. TPS series, surface-mount tantalum
Vishay Sprague 593D, 594D, 595D series, surface-mount tantalum
Sanyo OS-CON series, through-hole aluminum electrolytic

Paralleling Devices

Any number of MAX660 devices can be paralleled to reduce the output resistance. Each device must have its own pumping capacitor C1, while only one output capacitor COUT is required as shown in Figure 16. The composite output resistance is:

Equation 4. ROUT = ROUT of each MAX660 / Number of Devices
MAX660 10089807.png Figure 16. Lowering Output Resistance by Paralleling Devices

Cascading Devices

Cascading the MAX660s is an easy way to produce a greater negative voltage (as shown in Figure 17). If n is the integer representing the number of devices cascaded, the unloaded output voltage Vout is (−nVin). The effective output resistance is equal to the weighted sum of each individual device:

Equation 5. MAX660 eq5_snos405.png

A three-stage cascade circuit shown in Figure 18 generates −3 Vin, from Vin.

Cascading is also possible when devices are operating in doubling mode. In Figure 19, two devices are cascaded to generate 3 VIN.

An example of using the circuit in Figure 18 or Figure 19 is generating +15 V or −15 V from a +5-V input.

NOTE

The number of n is practically limited because the increasing of n significantly reduces the efficiency and increases the output resistance and output voltage ripple.

MAX660 10089808.png Figure 17. Increasing Output Voltage by Cascading Devices
MAX660 10089809.png Figure 18. Generating −3VIN From +VIN
MAX660 10089810.png Figure 19. Generating +3VIN From +VIN

Regulating Output Voltage

Output of the MAX660 can be regulated by use of a low-dropout regulator (such as LP2951). The whole converter is depicted in Figure 20. This converter can give a regulated output from −1.5 V to −5.5 V by choosing the proper resistor ratio:

Equation 6. MAX660 eq6_snos405.png

The error flag on pin 5 of the LP2951 goes low when the regulated output at pin 4 drops by about 5%. The LP2951 can be shut down by taking pin 3 high.

MAX660 10089811.png Figure 20. Combining MAX660 With LP2951 to Make a Negative Regulator

As shown in Figure 21 by operating MAX660 in voltage doubling mode and adding a linear regulator (such as LP2981) at the output, the user can get +5-V output from an input as low as +3 V.

MAX660 10089812.png Figure 21. Generating +5 V From +3-V Input Voltage

Application Curves

MAX660 1291111.png
Figure 22. Efficiency vs Load Current
MAX660 1291113.png
Figure 23. Efficiency vs Oscillator Frequency

Positive Voltage Doubler

MAX660 10089802.png Figure 24. MAX660 Voltage Doubler

Design Requirements

The MAX660 can operate as a positive voltage doubler (as shown in the Figure 24). The doubling function is achieved by reversing some of the connections to the device. The input voltage is applied to the GND pin with an allowable voltage from 2.5 V to 5.5 V. The V+ pin is used as the output. The LV pin and OUT pin must be connected to ground. The OSC pin cannot be driven by an external clock in this operation mode. The unloaded output voltage is twice of the input voltage and is not reduced by the forward drop of the diode (D1) .

Detailed Design Procedure

The Schottky diode D1 is only needed for start-up. The internal oscillator circuit uses the V+ pin and the LV pin (connected to ground in the voltage doubler circuit) as its power rails. Voltage across V+ and LV must be larger than 1.5 V to ensure the operation of the oscillator. During start-up, D1 is used to charge up the voltage at V+ pin to start the oscillator; also, it protects the device from turning on its own parasitic diode and potentially latching up. Therefore, the Schottky diode D1 must have enough current carrying capability to charge the output capacitor at start-up, as well as a low forward voltage to prevent the internal parasitic diode from turning on. A Schottky diode like 1N5817 can be used for most applications. If the input voltage ramp is less than 10V/ms, a smaller Schottky diode like MBR0520LT1 can be used to reduce the circuit size.

Split V+ in Half

Another interesting application shown in Figure 25 is to use the MAX660 as a precision voltage divider. Because the off-voltage across each switch equals VIN/2, the input voltage can be raised to 11 V.

MAX660 10089803.png Figure 25. Splitting VIN in Half