JAJSFO4B August   2017  – December 2018 OPA2810

PRODUCTION DATA.  

  1. 1 特長
  2. 2 アプリケーション
    1.     マルチチャネル・センサ・インターフェイス
  3. 3 概要
    1.     高調波歪みと周波数との関係
  4. 4 改訂履歴
  5. 5 Pin Configuration and Functions
    1.     Pin Functions
  6. 6 Specifications
    1. 6.1  Absolute Maximum Ratings
    2. 6.2  ESD Ratings
    3. 6.3  Recommended Operating Conditions
    4. 6.4  Thermal Information
    5. 6.5  Electrical Characteristics: 10 V
    6. 6.6  Electrical Characteristics: 24 V
    7. 6.7  Electrical Characteristics: 5 V
    8. 6.8  Typical Characteristics: VS = 10 V
    9. 6.9  Typical Characteristics: VS = 24 V
    10. 6.10 Typical Characteristics: VS = 5 V
    11. 6.11 Typical Characteristics: ±2.375 V to ±12 V Split Supply
  7. 7 Detailed Description
    1. 7.1 Overview
    2. 7.2 Functional Block Diagram
      1. 7.2.1 ESD Protection
    3. 7.3 Feature Description
      1. 7.3.1 OPA2810 Comparison
    4. 7.4 Device Functional Modes
      1. 7.4.1 Split-Supply Operation (±2.375 V to ±13.5 V)
      2. 7.4.2 Single-Supply Operation (4.75 V to 27 V)
  8. 8 Application and Implementation
    1. 8.1 Application Information
      1. 8.1.1 Selection of Feedback Resistors
      2. 8.1.2 Noise Analysis and the Effect of Resistor Elements on Total Noise
    2. 8.2 Typical Applications
      1. 8.2.1 Transimpedance Amplifier
        1. 8.2.1.1 Design Requirements
        2. 8.2.1.2 Detailed Design Procedure
      2. 8.2.2 Multichannel Sensor Interface
  9. 9 Power Supply Recommendations
  10. 10Layout
    1. 10.1 Layout Guidelines
      1. 10.1.1 Thermal Considerations
    2. 10.2 Layout Example
  11. 11デバイスおよびドキュメントのサポート
    1. 11.1 ドキュメントのサポート
      1. 11.1.1 関連資料
    2. 11.2 ドキュメントの更新通知を受け取る方法
    3. 11.3 コミュニティ・リソース
    4. 11.4 商標
    5. 11.5 静電気放電に関する注意事項
    6. 11.6 Glossary
  12. 12メカニカル、パッケージ、および注文情報

パッケージ・オプション

メカニカル・データ（パッケージ｜ピン）
サーマルパッド・メカニカル・データ
発注情報

8.1.1 Selection of Feedback Resistors

The OPA2810 is a classic voltage feedback amplifier with each channel having two high-impedance inputs and a low-impedance output. Standard application circuits include the noninverting and inverting gain configurations as Figure 65 and Figure 66 show. The DC operating point for each configuration is level-shifted by the reference voltage VREF which is typically set to midsupply in single-supply operation. VREF is often connected to ground in split-supply applications.

OPA2810 noninv_amp.gifFigure 65. Noninverting Amplifier
OPA2810 inv_amp.gifFigure 66. Inverting Amplifier

The closed-loop gain of an amplifier in noninverting configuration is shown in Equation 1.

Equation 1. OPA2810 OPA2810_NI_Gain.gif

The closed-loop gain of an amplifier in an inverting configuration is shown in Equation 2.

Equation 2. OPA2810 OPA2810_Inv_Gain.gif

The magnitude of the low-frequency gain is determined by the ratio of the magnitudes of the feedback resistor (RF) and the gain setting resistor RG. The order of magnitudes of the individual values of RF and RG offer a trade-off between amplifier stability, power dissipated in the feedback resistor network, and total output noise. The feedback network increases the loading on the amplifier output. Using large values of the feedback resistors reduces the power dissipated at the amplifier output. On the other hand, this increases the inherent voltage and amplifier current noise contribution seen at the output while lowering the frequency at which a pole occurs in the feedback factor (β). This pole causes a decrease in the phase margin at zero-gain crossover frequency and potential instability. Using small feedback resistors increases power dissipation and also degrades amplifier linearity due to a heavier amplifier output load. Figure 67 shows a representative schematic of the OPA2810 in an inverting configuration with the input capacitors shown.

OPA2810 schem-Cin_Eq.gifFigure 67. Inverting Amplifier with Input Capacitors

The effective capacitance seen at the amplifier's inverting input pin is shown in Equation 3 which forms a pole in β at a cut-off frequency of Equation 4.

Equation 3. OPA2810 OPA2810_CinEq.gif
Equation 4. OPA2810 eq-OPA2810_Beta_Pole.gif

where:

  • CCM is the amplifier common-mode input capacitance
  • CDIFF is the amplifier differential input capacitance
  • and, CPCB is the PCB parasitic capacitance.

For low-power systems, greater the values of the feedback resistors, the earlier in frequency does the phase margin begin to reduce and cause instability. Figure 68 and Figure 69 illustrate the loop gain magnitude and phase plots, respectively, for the OPA2810 simulation in TINA-TI configured as an inverting amplifier with values of feedback resistors varying by orders of magnitudes.

OPA2810 D801_App_Resistor_Selection_Loop_Gain.gifFigure 68. Loop-Gain vs. Frequency for Circuit of Figure 67
OPA2810 D802_App_Resistor_Selection_Loop_Phase.gifFigure 69. Loop-Gain Phase vs. Frequency for Circuit of Figure 67

A lower phase margin results in peaking in the frequency response and lower bandwidth as Figure 70 shows, which is synonymous with overshoot and ringing in the pulse response results. The OPA2810 offers a flat-band voltage noise density of 6 nV/√Hz. TI recommends selecting an RF so the voltage noise contribution does not exceed that of the amplifier. Figure 71 shows the voltage noise density variation with value of resistance at 25°C. A 2-kΩ resistor exhibits a thermal noise density of 5.75 nV/√Hz which is comparable to the flatband noise of the OPA2810. Hence, TI recommends using an RF lower than 2 kΩ while being large enough to not dissipate excessive power for the output voltage swing and supply current requirements of the application. The Noise Analysis and the Effect of Resistor Elements on Total Noise section shows a detailed analysis of the various contributors to noise.

OPA2810 D806_App_Resistor_Selection_Noise_Gain.gifFigure 70. Closed-Loop Gain vs. Frequency for Circuit of Figure 67
OPA2810 D803_App_Resistor_Selection_Resistor_Noise.gifFigure 71. Thermal Noise Density vs Resistance