SLUS223G April   1997  – July 2022

PRODUCTION DATA

1. Features
2. Applications
3. Description
4. Revision History
5. Device Comparison Table
6. Pin Configuration and Functions
7. Specifications
8. Detailed Description
1. 8.1 Overview
2. 8.2 Functional Block Diagrams
3. 8.3 Feature Description
4. 8.4 Device Functional Modes
9. Application and Implementation
1. 9.1 Application Information
2. 9.2 Typical Application
1. 9.2.1 Design Requirements
2. 9.2.2 Detailed Design Procedure
3. 9.2.3 Application Curves
10. 10Power Supply Recommendations
11. 11Layout
1. 11.1 Layout Guidelines
2. 11.2 Layout Example
12. 12Device and Documentation Support
13. 13Mechanical, Packaging, and Orderable Information

• D|8
• D|14
• P|8
• D|8
• D|14

#### 9.2.2.3 Transformer Inductance and Peak Currents

For this design example, the transformer magnetizing inductance is selected based upon the CCM condition. An inductance value that allows the converter to stay in CCM over a wider operating range before transitioning into discontinuous current mode is used to minimize losses due to otherwise high currents and also to decrease the output ripple. The design of the transformer in this example sizes the inductance so the converter enters CCM operation at approximately 10% load and minimum bulk voltage to minimize output ripple.

The inductor, LP for a CCM flyback can be calculated using Equation 17.

Equation 17. In Equation 17, the input power, PIN, is estimated by dividing the maximum output power, POUT, by the target efficiency, η, and fSW is the switching frequency; for the UC2842 the switching frequency is equal to the oscillator frequency and is set to 110 kHz. Therefore, the transformer inductance should be approximately 1.8 mH; a 1.5-mH inductance is chosen as the magnetizing inductance value for this design.

Based on calculated inductor value and the switching frequency, the current stress of the MOSFET and output diode can be calculated.

The peak current in the primary-side MOSFET of a CCM flyback can be calculated as shown in Equation 18.

Equation 18. The MOSFET peak current is 1.36 A. The RMS current of the MOSFET is calculated to be 0.97 A as shown in Equation 19. Therefore, IRFB9N65A is selected to be used as the primary-side switch.

Equation 19. The output diode peak current is equal to the MOSFET peak current reflected to the secondary side.

Equation 20. The diode average current is equal to the total output current, 4 A; combined with a required 60-V rating and 13.6-A peak current requirement, a 48CTQ060-1 is selected for the output diode.